Clock generator and delta-sigma modulater thereof

ABSTRACT

A clock generator is illustrated. The clock generator mentioned above includes a multimodulus frequency divider and a delta-sigma modulator. The multimodulus frequency divider is archived by switching the phase thereof. The multimodulus frequency divider increases the operating frequency of the clock generator effectively, and has a characteristic with half period resolution for reducing the jitter of an output clock signal when its spectrum is spread. Besides, the delta-sigma modulator increases the accuracy of the triangle modulation and reduces error of quantization by adding a few components therein. Thus, the clock generator could be expanded to a programmable clock generator.

CROSS-REFERENCE TO RELATED APPLICATION

This application is a divisional of an application Ser. No. 12/391,263,filed on Feb. 24, 2009, now U.S. Pat. No. 7,924,965, which claims thepriority benefit of Taiwan application serial no. 97151134, filed Dec.26, 2008. The entirety of each of the above-mentioned patentapplications is hereby incorporated by reference herein and made a partof this specification.

TECHNICAL FIELD

The present invention generally relates to a clock generator, and moreparticularly to a clock generator for providing a spread spectrum outputclock signal.

BACKGROUND

In the field of the high speed transmission, the phenomenon in thesystem, such as error occurrence or abnormally functioning, may happendue to the period signal having the centralized and strong energy. Theenergy is a form of electromagnetism, and also called as electromagneticinterference (EMI). Recently, a technology of spectrum expansion is usedto reduce the electromagnetic interference, which is also called as aspread spectrum technology. The spread spectrum technology makes thefrequency of the clock signal distributed in a certain range, so as todiverse the energy of the clock signal, and to reduce the energy of theinterference. Generally, the clock generators using the spread spectrumtechnology can be divided into three categories.

Referring to FIGS. 1A-1C and FIGS. 1A-1C are block diagrams ofconventional clock generators of three categories. The spread spectrumclock generator in FIG. 1A receives the input clock signal FIN, and usesthe low pass filter (LPF) 110 to perform a direct modulation. Then thespread spectrum clock generator changes the frequency of the outputclock signal FOUT by changing the control voltage generated by the lowpass filter 110. Most of the spread spectrum clock generators of thiscategory need passive components of the larger size, so as to obtain thebetter stability control. However the passive components of the largersize consume the larger area and cost, and have the higher sensitivityfor the process, the temperature and the voltage.

In FIG. 1B, the delta-sigma phase switching or the phase compensation isused to construct the spread spectrum clock generator 120, and thus thespread spectrum clock generator 120 can adjust the frequency of theoutput clock signal. The spread spectrum clock generator of thiscategory uses the little phase deviation to perform a modulation, andtherefore it has the smaller jitter. However, while operating in thehigh frequency condition, it is hard to obtain the accurate phase due tothe effect of the parasitical capacitor and the parasitical resistor onthe unmatched winding wire.

In addition, the spread spectrum clock generator in FIG. 1C is thespread spectrum clock generator of the third category which uses thefractional frequency dividing to perform a modulation. The multimodulusfrequency divider 130 thereof has two or more than two moduluses andmultiples the frequency of the output clock signal FOUT with a fractionnumber via the switching control of a certain ratio made by the spreadspectrum modulator 140.

Take the spread spectrum clock generator in FIG. 1C as an example, theswitch between the several moduluses is needed when the fractionalfrequency dividing is processed. The switch between the severalmoduluses is occurred in the fixed period. Though the effect of theaverage fractional frequency dividing is achieved, the phase detector150 generates an error signal at the moment of the switch between theseveral moduluses. The error signal will affect the voltage controlledoscillator 160, change the frequency of the output clock signal FOUT,and generate a fractional spike in the spectrum.

Moreover, the spread spectrum modulator 140 used to control themultimodulus frequency divider 130 is usually constructed by thedelta-sigma modulator, and the effect of the spread spectrum isdetermined by the bit width of the delta-sigma modulator. The higher thebit width is, and the smaller the quantization error can be obtained.Referring to FIG. 2, FIG. 2 is a wave diagram of the spread spectrumcontrol voltage signal. The larger the bit width of the sigma-deltamodulator is, the higher resolution thereof can be obtained, and thesmoother the triangle wave 210 is. Therefore, a better effect of thespread spectrum is achieved.

SUMMARY OF THE INVENTION

In exemplary embodiments consistent with the present invention, there isprovided a sigma-delta modulator, and the sigma-delta modulatorcomprises at least a sigma-delta modulating unit. The sigma-deltamodulating unit comprises at least a frequency dividing circuit, atleast an accumulator, at least a pulse width adjusting circuit, and atleast a data calculating device. The frequency dividing circuit receivesan input clock signal, and divides a frequency of the input clocksignal, so as to generate a frequency dividing clock signal. Theaccumulator is coupled to the frequency dividing circuit, and is used toreceive the frequency dividing clock signal, and to accumulate afractional part input signal in response to the frequency dividing clocksignal, so as to generate a quantized output signal and an outputoverflow signal. The pulse width adjusting circuit is coupled to theaccumulator. The pulse width adjusting circuit is used to receive theoutput overflow signal and the frequency dividing clock signal, and toadjust the pulse width of the output overflow signal in response to aperiod of the frequency dividing clock signal, so as to generate a widthadjusted output overflow signal. The data calculating device is coupledto the pulse width adjusting circuit, and is used to take the widthadjusted output overflow signal and an integral part input signal intoan algorithmic calculation, so as to generate an control signal.

In exemplary embodiments consistent with the present invention, there isprovided another one clock generator which is constructed by a phaselocked loop circuit and used to generate an output clock signal inresponse to an input clock signal and a feedback clock signal. Thefeedback clock signal and the output clock signal have a multiplerelation, and the clock generator comprises the multimodulus frequencydivider and the sigma-delta modulator mentioned above.

It is to be understood that both the foregoing general description andthe following detailed description are exemplary, and are intended toprovide further explanation of the invention as claimed.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings are included to provide a furtherunderstanding of the invention, and are incorporated in and constitute apart of this specification. The drawings illustrate embodiments of theinvention and, together with the description, serve to explain theprinciples of the invention.

FIGS. 1A-1C are block diagrams of conventional clock generators of threecategories.

FIG. 2 is a wave diagram of the spread spectrum control voltage signal.

FIG. 3 is a block diagram of a clock generator provided by theembodiment of the present invention.

FIG. 4A is a circuit diagram of the multimodulus frequency divider 340according to one embodiment of the present invention.

FIG. 4B is a waveform diagram of the waveforms of the multimodulusfrequency divider 340.

FIG. 5A is a circuit diagram of the sigma-delta modulator 350 accordingto one embodiment of the present invention.

FIG. 5B is a circuit diagram of the accumulator 352 in the sigma-deltamodulator 350 according to one embodiment of the present invention.

FIG. 5C is a waveform diagram of the waveforms in the accumulator 352.

FIG. 5D is a circuit diagram of the sigma-delta modulator 350 accordingto another one embodiment of the present invention.

FIG. 5E is a circuit diagram of a device for generating the referenceclock signals CKR1, CKR2, and the input clock signal in FIG. 5Daccording to one embodiment of the present invention.

FIG. 6 is a circuit diagram of a second order sigma-delta modulatoraccording to one embodiment of the present invention.

FIG. 7 is a circuit diagram of a M order sigma-delta modulator accordingto one embodiment of the present invention.

DESCRIPTION OF THE EMBODIMENTS

Reference will now be made in detail to exemplary embodiments, examplesof which are illustrated in the accompanying drawings. The followingdescription refers to the accompanying drawings in which the samenumbers in different drawings represent the same or similar elementsunless otherwise represented. The implementations set forth in thefollowing description of exemplary embodiments consistent with thepresent invention do not represent all implementations consistent withthe invention. Instead, they are merely examples of systems and methodsconsistent with aspects related to the invention as recited in theappended claims.

In exemplary embodiments consistent with the present invention providesa multimodulus frequency divider which is used to generate a relation ofthe output multimodulus frequency dividing signal and the input signal.

In exemplary embodiments consistent with the present invention providesa sigma-delta modulator which is used to calculate an integral partinput signal and a fractional part input signal, so as to generate anoutput overflow signal.

In exemplary embodiments consistent with the present inventionrespectively provide two clock generators which are used to dynamicallyadjust the frequency of the output clock signal.

First, referring to FIG. 3, FIG. 3 is a block diagram of a clockgenerator provided by the embodiment of the present invention. The clockgenerator 300 is constructed by the phase locked loop (PLL) circuit, andcomprises a phase detection and integration device 310, a loop filter320, a voltage controlled oscillator (VCO) 330, a multimodulus frequencydivider 340, a sigma-delta modulator 350, and a waveform generator 360.The phase detection and integration device 310 receives the input clocksignal FIN and the feedback clock signal FBK, and detects the deviationbetween both of them. When a frequency of the input clock signal FIN ishigher than that of the feedback clock signal, the internal end of thephase detection and integration device 310 generates a pulse with apositive value; by contrast, when the frequency of the input clocksignal FIN is lower than that of the feedback clock signal, the internalend of the phase detection and integration device 310 generates thepulse with a negative value.

The phase detection and integration device 310 integrates the pulsesgenerated by the foregoing manner, so as to generate a differentialvoltage VD, wherein the integration is usually done by the process ofcharge pump. Then, the differential voltage VD is input into the loopfilter 320, so as to generate a control voltage VT, wherein the controlvoltage is an input of the voltage controlled oscillator 330. The chargepump and the loop filter are known and understood by the person havingthe general acknowledge in the field, and thus they are not described indetail herein.

The multimodulus frequency divider 340 is coupled to the voltagecontrolled oscillator 330, and is used to receive the output clocksignal FOUT, so as to generate a feedback clock signal FBK. The outputclock signal FOUT and the feedback clock signal have a multiplerelation, and the multiple relation is determined a control signal CTRL.When the clock generator 300 operates stably, the input clock signal FINand the output clock signal FOUT have the multiple relation same as thatof the output clock signal FOUT and the feedback clock signal FBK. Theclock generator dynamically adjusts the multiple relation in response tothe control signal CTRL, so as to change the frequency of the outputclock signal FOUT, and to achieve the spread spectrum function.

The sigma-delta modulator 350 is coupled to the multimodulus frequencydivider 340, and is used to determine the control signal which is usedto determine the multiple relation. The sigma-delta modulator 350receives a signal set of an integral part input signal IP and afractional part input signal FP. The sigma-delta modulator 350 isfurther coupled to the waveform generator 360, and the waveformgenerator 360 is used to provide the fractional signal FP of thefrequency dividing modulus.

Next, different embodiments of the multimodulus frequency divider 340and the sigma-delta modulator 350 in the clock generator 300 areprovided, so as to illustrate the operation of the clock generator 300.

Referring to FIG. 4A, FIG. 4A is a circuit diagram of the multimodulusfrequency divider 340 according to one embodiment of the presentinvention. The multimodulus frequency divider 340 comprises a pluralityof multimodulus frequency dividing units. In this embodiment, themultimodulus frequency divider 340 comprises four multimodulus frequencydividing units 341-344, however the number of the multimodulus frequencydividing units is not limited thereto in the present invention. Thestructures of the multimodulus frequency dividing units 341-344 aresimilar to each other. Take the multimodulus frequency dividing unit 341as an example, the multimodulus frequency dividing unit 341 comprises anand-gate AND1, selector 3411, a delay buffer 3415, a frequency divider3412, a D flip-flop 3413 and a frequency divider 3414.

The delay buffer 3415 constructs an input phase synchronization unit,and the selector 3411 constructs an input phase selection unit. Thefrequency divider 3412 constructs a frequency dividing and phasegenerating unit, and the D flip-flop 3413 constructs a phase selectionsignal synchronization unit. The frequency divider 3414 constructs aphase state selection unit, and the and-gate AND1 constructs a phaseselection control unit.

In addition, the input phase synchronization unit is used to receive aplurality of input signals, and to synchronize the received inputsignals, so as to generate a plurality of synchronous input signals, andthe phase differences (i.e. phase errors) between these synchronousinput signals are not equal to zero. The input phase selection unitreceives these synchronous input signals and a selection signal, andselects a phase of one synchronous input signal among these synchronousinput signals in response to the selection signal, so as to generate aselected synchronous input signal. The frequency dividing and phasegenerating unit receives the selected synchronous input signal, anddivides a frequency of the selected synchronous input signal, so as toobtain an output multimodulus frequency dividing signal. The phaseselection control unit receives the output multimodulus frequencydividing signal and a control signal, and takes the output multimodulusfrequency dividing signal and the control signal into a logiccalculation, so as to generate a feedback signal. The phase stateselection unit changes a state of the selection signal into anotherstate or maintains the state of the selection signal in response towhether the feedback signal is triggered or not, so as to generate arecording phase signal. Last the phase selection signal synchronizationunit synchronizes the recording phase signal in response to one of theinput signals, so as to generate the selection signal.

The selector 3411 in the first multimodulus frequency dividing unit 341receives the output clock signal FOUT and the inversed output clocksignal FOUTB of the clock generator 300. The phase deviation of theoutput clock signal FOUT and the inversed output clock signal FOUTB is180° rather than 0°. The output clock signal FOUT and the inversedoutput clock signal FOUTB are input into the selector 3411 via the delaybuffer 3415. The output end of the selector 3411 is coupled to thefrequency divider 3412, and is used to output the selection clock signalMFOUT. The selection end of the selector 3411 is coupled to the Dflip-flop 3413. Furthermore, the D flip-flop 3413 is coupled to theoutput end of the frequency divider 3414, and the input end of thefrequency divider 3414 is coupled to the output end of the and-gateAND1. One input end of the and-gate AND1 is coupled to the controlsignal CTRL₀, and the other end of the and-gate AND1 is coupled to theinput ends of the and-gate AND2-AND4 for receiving the feedback clocksignal FBK. The feedback clock signal FBK is generated by the output endof the frequency divider 3442 in the last multimodulus frequencydividing unit 344.

In addition, the input end of each selector in the multimodulusfrequency dividing units 341-344 is further coupled to the delay bufferin cascade. Take the multimodulus frequency dividing unit 341 as anexample; the input end of the selector 3411 is coupled to the delaybuffer 3415 in cascade. The delay buffer 3415 is constructed by twodelay units BUF1 and BUF2, and the delay units BUF1 and BUF2 are used torespectively delay the transmitting time to the selector 3411 of theoutput clock signal FOUT and that of the inversed output clock signalFOUTB.

Regarding detail of the operation in the multimodulus frequency divider340, the dividing factor is changed from 2 to 2.5 by switching theoutput clock signal FOUT and that of the inversed output clock signalFOUTB. Referring to FIG. 4B, FIG. 4B is a waveform diagram of thedivider unit 341 in multi-modulus divider 340. To know the operationconcept of the single stage, such as the multimodulus frequency dividingunit 341, please refer to FIGS. 4A and 4B. The and-gate AND1 in themultimodulus frequency dividing unit 341 is used to determine whetherthe control phase is switched. When the control signal CTRL₀ received bythe and-gate AND1 is logic low, “0”, the feedback signal FBK received bythe and-gate AND1 is not transmitted into the multimodulus frequencydividing unit 341. That is, the phase of the output clock signal FOUT isnot switched. When the control signal CTRL₀ received by the and-gateAND1 is logic high, “1”, the feedback signal FBK received by theand-gate AND1 is transmitted into the multimodulus frequency dividingunit 341. That is, the phase of the output clock signal FOUT isswitched.

In the embodiment, the frequency divider 3414 is used to divide thefrequency of its input by 2, so as to record and change the selectedphase. The D flip-flop 3413 is a flip-flop for synchronization. The Dflip-flop 3413 synchronizes the phase of the selection signal with theinput signal phases. The circuit of delay buffer 3415 is similar to thecircuit from the input clock end to the output end of the D flip-flop3413, and the delay buffer 3415 is used to synchronize the phases ofinput signals with the selection signal phase. The frequency divider3412 divide the frequency of the output signal MFOUT output form theselector 3411.

In the single stage case with the multimodulus frequency dividing unit341, when the control signal CTRL₀ is logic high, “1”, the period of theoutput clock signal FOUT1 of the frequency divider 3412 is 2.5 times theperiod of the output clock signal FOUT, and it is shown in FIG. 4B.

It is noted that, due to the cascade connection of the multimodulusfrequency dividing unit 341-344, the phase switching variation providedby the frequency divider 3422 is two times the phase switching variationprovided by the frequency divider 3412 when the frequency dividers 3412and 3422 have the dividing factor of 2. That is, the phase switchingvariation provided by the frequency divider 3422 is one period, and thephase switching variations provided by the other frequency dividers canbe deduced in this manner.

Accordingly, a relation between the frequency dividing factor DN and thecontrol signals CTRL₀-CTRL_(N-1) is obtained and shown as:DN=2^(N)+{2^(N-1)×CTRL_(N-1)+ . . . +2¹×CTRL₁+2⁰×CTRL₀}×0.5

Therefore, in the embodiment, the multimodulus frequency divider 340(N=4) has a half period resolution for reducing the jitter of thecontrol voltage to be 0.5 times when its spectrum is spread. Thus theoutput jitter of the voltage controlled oscillator is reduced. When thecontrol signals CTRL₀-CTRL₃ are respectively equal to 1, 0, 0, and 0,the frequency dividing factor DN is 16+1×0.5=16.5.

Next, referring to FIG. 5A, FIG. 5A is a circuit diagram of thesigma-delta modulator 350 according to one embodiment of the presentinvention. The sigma-delta modulator 350 comprises a frequency divider351, an accumulator 352, an and-gate AND5 which forms a pulse widthadjusting circuit, and a data calculating device 354. The frequencydivider receives a reference clock signal CKR and divides a frequency ofthe reference clock signal CKR, so as to generate a frequency dividingreference clock signal DCKR and an inversed frequency dividing referenceclock signal DCKRB. In the embodiment, the frequency divider 351 isimplemented by a D flip-flop connected as a T flip-flop. Thus this Dflip flop functions as a frequency divider for dividing the frequency ofthe reference clock signal CKR with a dividing factor of 2. Theaccumulator 352 receives a fractional part input signal FP, andaccumulates the fractional part input signal FP in response to theinversed frequency dividing reference clock signal DCKRB, so as togenerate a quantized output signal QOUT and an output overflow signalOV. The output end of the and-gate AND5 is coupled to the datacalculating device 354. In the embodiment, the data calculating device354 is a subtractor, which is used to subtract the output overflowsignal OV generated by the accumulator 352 from the integral part inputsignal IP.

To understand detail of the operation of the accumulator 352, pleasesimultaneously see FIGS. 5A and 5B. FIG. 5B is a circuit diagram of theaccumulator 352 in the sigma-delta modulator 350 according to oneembodiment of the present invention. In the embodiment, the accumulator352 comprises a D flip-flop 3521 and an adder 3522. It is noted that theaccumulator 352 cooperates with the frequency divider 351, and theyequivalently function as an accumulator which quantization resolution isthat of the accumulator 352 plus one bit. That is, the accumulator 352of N bits will be equivalent to the accumulator of N+1 bits. Theinversed frequency dividing reference clock signal DCKRB received by theaccumulator 352 herein is generated from the reference clock signal CKR,wherein the frequency of the inversed frequency dividing reference clocksignal DCKRB is divided from the frequency of the reference clock signalCKR. Since the frequency of the inversed frequency dividing referenceclock signal DCKRB is the half of the reference clock signal CKR, thepulse width TCOUT5 of the output overflow signal OV is doubled. Then theand-gate AND5 regulates the pulse width of the output overflow signal OVto be same as the pulse width of the output overflow signal output fromthe accumulator of N+1 bits (i.e. the output signal TCOUT5H of theand-gate AND5). Hence, the accuracy of the N bits is equivalent to thatof the N+1 bits, and the operating frequency of the clock generator isreduced, so as to save power consumption. The enhancing multiple of theaccuracy of the equivalent technology is a positive integer which islarger than 1, and the effect of the accuracy enhancing is determined bythe input frequency dividing modulus of the reference clock signal CKR,wherein the relation formulation is shown as:

${{Accuracy} = \frac{FP}{2^{N} \times M}},$N is the data width of the original accumulator, and M is the inputfrequency dividing modulus of the frequency divider of the referenceclock signal CKR. It is noted that the value of the factional part inputsignal FP is limited to be 2^(N). Therefore, the maximum modulatingfactor of the sigma-delta modulator is not equal to 1, but2^(N)/(2^(N)×M).

Please see FIG. 5C, FIG. 5C is a waveform diagram of the waveforms inthe accumulator 352. The signal COUT5 is the output overflow signalwhich is generated in response to the reference clock signal CKR by theoriginal accumulator of 5 bits, and the signal COUT6 is the outputoverflow signal which is generated in response to the reference clocksignal CKR by the original accumulator of 6 bits. The frequency offrequency dividing reference clock signal DCKR is the frequency of thereference clock signal divided by 2. The signal TCOUT5 is the outputoverflow signal generated by the inversed frequency dividing referenceclock signal DCKRB, and thus the pulse width of the signal TCOUT5 istwice of the inversed frequency dividing reference clock signal DCKRB.Thus the and-gate AND5 is particularly used to change the pulse width ofTCOUT5 to the half by and with DCKR, so as to obtain the waveform of thewidth adjusted output overflow signal TCOUT5H. The waveform of the widthadjusted output overflow signal TCOUT5H is same as that of the signalCOUT6.

Please see FIG. 5D, FIG. 5D is a circuit diagram of the sigma-deltamodulator 350 according to another embodiment of the present invention.In the embodiment, the frequencies reference clock signals CKR1 and CKR2 are respectively the half and the quarter frequencies of the referenceclock signal CKR. A multiplexer 355 and an and-gate AND 6 are insertedbetween accumulator 352 and the data calculating device 354 of thesigma-delta modulator 350. The multiplexer 355 is coupled between theand-gates (AND5 and AND6) and the data calculating device 354, and isused to select one of the width adjusted output overflow signalsgenerated by the and-gates (AND5 and AND6, so as to output the selectedone to the data calculating device 354. Meanwhile, a selector is addedat the front of the end for receiving the input clock signal SCKR of theaccumulator 352, and therefore the frequency dividing modulus can beselected. Accordingly, the equivalent bit width is changed by selectingthe clock frequency rate and the pulse width of the output overflowsignal of the sigma-delta modulator 350, thus the equivalent bit widthof the sigma-delta modulator 350 is programmable, and the programmablespread spectrum function is achieved.

In addition, regarding the generation of the reference clock signal CKR1and CKR2, please refer to FIG. 5E, and FIG. 5E is a circuit diagram of adevice for generating the reference clock signals CKR1, CKR2, and theinput clock signal in FIG. 5D according to one embodiment of the presentinvention. The frequency of the reference clock signal CKR1 is dividedfrom the input clock signal FIN by the frequency divider 356, and thefrequency of the reference clock signal CKR2 is divided from thereference clock signal CKR1 by the frequency divider 357. In addition,the multiplexer 358 is coupled to the accumulator, and is used toreceive the frequency dividing clock signals CKR1, CKR2, and the inputclock signal FIN. The multiplexer 358 selects one of the reference clocksignals CKR1, CKR2, the input clock signal FIN, and the system groundGND, so as to generate the input clock signal SCKR, and then the inputclock signal SCKR is transmitted to the accumulator.

Next, a second order sigma-delta modulator is described, wherein thesecond order sigma-delta modulator is constructed by the two sigma-deltamodulation unit. Referring to FIG. 6, FIG. 6 is a circuit diagram of asecond order sigma-delta modulator according to one embodiment of thepresent invention. The second order sigma-delta modulator comprises twoaccumulators with N bits 710 and 720, and both of the accumulators withN bits 710 and 720 are connected in a cascade structure. Regarding theaccumulator 720 of the second stage, a data calculating device 760, anand-gate AND8, and a D flip-flop 740 are added to process the outputoverflow signal generated by the accumulator 720. The output overflowsignal generated by the accumulator 720 is transmitted to the and-gateAND8, so as to adjust the pulse width of the output overflow signal. TheD flip-flop 740 is used to delay the output overflow signal, and thedata calculating device 760 subtracts the output overflow signal fromthe delayed output overflow signal, so as to obtain a deviation result.The deviation result is transmitted to the data calculating device ofthe next stage, so as to perform an adding operation on the deviationresult. Thus, the structure makes the sigma-delta modulator with N bitsequivalent to the sigma-delta modulator with N+1 bits.

Next, the accumulators of the sigma-delta modulator can be connected tomake it have more orders or only one order. Referring to FIG. 7, FIG. 7is a circuit diagram of an M order sigma-delta modulator according toone embodiment of the present invention. The sigma-delta modulator 800is formed by the cascade connection of the sigma-delta modulating units.The accumulators 8101-810M are connected in cascade by turns. Therefore,the function of expanding the sigma-delta modulating order is achieved,and the ability of the regulating the quantization error is enhanced.

Accordingly, the embodiment adapts the multimodulus frequency dividerand the sigma-delta modulator with enhanced accuracy to improve theaccuracy and the stability of the clock generator. The multimodulusfrequency divider implemented by switching the phase thereof has thenon-integral resolution, thus the operating frequency of the clockgenerator is increased, and the output jitter caused by spreading thespectrum thereof is reduced.

It will be apparent to those skilled in the art that variousmodifications and variations can be made to the structure of the presentinvention without departing from the scope or spirit of the invention.In view of the foregoing descriptions, it is intended that the presentinvention covers modifications and variations of this invention if theyfall within the scope of the following claims and their equivalents.

1. A sigma-delta modulator, comprising: at least a frequency dividingcircuit, receiving an input clock signal, and dividing a frequency ofthe input clock signal, so as to generate at least a frequency dividingclock signal; at least an accumulator, coupled to the frequency dividingcircuit, receiving the frequency dividing clock signal, and accumulatinga fractional part input signal in response to the frequency dividingclock signal, so as to generate a quantized output signal and an outputoverflow signal; at least a pulse width adjusting circuit, coupled tothe accumulator, receiving the output overflow signal and the frequencydividing clock signal, and adjusting a pulse width of the outputoverflow signal in response to a period of the frequency dividing clocksignal, so as to generate a width adjusted output overflow signal; andat least a data calculating device, coupled to the pulse width adjustingcircuit, taking the width adjusted output overflow signal and anintegral part input signal into an algorithmic calculation, so as togenerate a control signal.
 2. The sigma-delta modulator according toclaim 1, wherein the pulse width adjusting circuit is an and-gate, inputends of the and-gate respectively receive the output overflow signal andthe frequency dividing clock signal, and an output end of the and-gateoutputs the width adjusted output overflow signal.
 3. The sigma-deltamodulator according to claim 1, wherein the control signal generated bythe data calculating device outputs is obtained by subtracting the widthadjusted output overflow signal from the integral part input signal. 4.The sigma-delta modulator according to claim 1, wherein when thesigma-delta modulator comprising the pulse width adjusting circuits, thesigma-delta modulator further comprises: a first multiplexer, coupledbetween the pulse width adjusting circuits and the data calculatingdevice, selecting one of the output overflow signals generated by thepulse width adjusting circuits, and transmitting the selected outputoverflow signal to the data calculating device.
 5. The sigma-deltamodulator according to claim 4, wherein when the sigma-delta modulatorcomprising the frequency dividers, the sigma-delta modulator furthercomprises: a second multiplexer, coupled between the accumulators andthe frequency dividing clock signals, selecting one of the frequencydividing clock signals, and to transmitting the selected frequencydividing clock signal to the accumulators.
 6. A clock generator,constructed by a phase locked loop circuit, generating an output clocksignal in response to the an input clock signal and a feedback clocksignal, the feedback clock signal and the output clock signal have amultiple relation, and the clock generator comprises: a multimodulusfrequency divider, generating the multiple relation in response to acontrol signal; and a sigma-delta modulator, the sigma-delta modulatorcomprises a sigma-delta modulating unit, and the sigma-delta modulatingunit comprises: a frequency dividing circuit, receiving an input clocksignal and generating a frequency dividing clock signal according to theinput clock signal; an accumulator, coupled to the frequency dividingcircuit, used to receive the frequency dividing clock signal, and toaccumulate a fractional part input signal in response to the frequencydividing clock signal, so as to generate a quantized output signal andan output overflow signal; a pulse width adjusting circuit, coupled tothe accumulator, used to receive the output overflow signal and adjuststhe pulse width of the output overflow signal in response to a period ofthe frequency dividing clock signal, so as to generate a width adjustedoutput overflow signal; and a data calculating device, coupled to thepulse width adjusting circuit, used to take the width adjusted outputoverflow signal and an integral part input signal into an algorithmiccalculation, so as to generate the control signal.
 7. The clockgenerator according to claim 6, wherein the pulse width adjustingcircuit is an and-gate, input ends of the and-gate respectively receivethe output overflow signal and the frequency dividing clock signal, andan output end of the and-gate outputs the width adjusted output overflowsignal.
 8. The clock generator according to claim 6, wherein the controlsignal generated by the data calculating device outputs is obtained bysubtracting the width adjusted output overflow signal from the integralpart input signal.
 9. The clock generator according to claim 6, whereinwhen the sigma-delta modulator comprising the pulse width adjustingcircuits, the sigma-delta modulator further comprises: a firstmultiplexer, coupled between the pulse width adjusting circuits and thedata calculating device, selecting one of the output overflow signalsgenerated by the pulse width adjusting circuits, and transmitting theselected output overflow signal to the data calculating device.
 10. Theclock generator according to claim 9, wherein when the sigma-deltamodulator comprising the frequency dividers, the sigma-delta modulatorfurther comprises: a second multiplexer, coupled between theaccumulators and frequency dividing clock signals, selecting one of thefrequency dividing clock signals, and to transmitting the selectedfrequency dividing clock signal to the accumulators.